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Part Number HIP6603BCB-T
Manufacturer Intersil
Datasheet HIP6603BCB-T Datasheet
Package 8-SOIC (0.154", 3.90mm Width)
In Stock 5,844 piece(s)
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HIP6603BCB-T Specifications

CategoryIntegrated Circuits (ICs) - PMIC - Gate Drivers
Datasheet HIP6603BCB-TDatasheet
Package8-SOIC (0.154", 3.90mm Width)
Driven ConfigurationHalf-Bridge
Channel TypeSynchronous
Number of Drivers2
Gate TypeN-Channel MOSFET
Voltage - Supply10.8 V ~ 13.2 V
Logic Voltage - VIL, VIH-
Current - Peak Output (Source, Sink)-
Input TypeNon-Inverting
High Side Voltage - Max (Bootstrap)15V
Rise / Fall Time (Typ)20ns, 20ns
Operating Temperature0°C ~ 125°C (TJ)
Mounting TypeSurface Mount
Package / Case8-SOIC (0.154", 3.90mm Width)
Supplier Device Package8-SOIC

HIP6603BCB-T Datasheet

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FN9072 Rev 9.00 December 10, 2015 HIP6601B, HIP6603B, HIP6604B Synchronous Rectified BuckMOSFET Drivers DATASHEET NOT RECOMMENDED FOR NEW DESIGNSNO RECOMMENDED REPLACEMENTcontact our Technical Support Center at1-888-INTERSIL or HIP6601B, HIP6603B and HIP6604B are high- frequency, dual MOSFET drivers specifically designed to drive two power N-Channel MOSFETs in a synchronous rectified buck converter topology. These drivers combined with a HIP63xx or the ISL65xx series of Multi-Phase Buck PWM controllers and MOSFETs form a complete core- voltage regulator solution for advanced microprocessors. The HIP6601B drives the lower gate in a synchronous rectifier to 12V, while the upper gate can be independently driven over a range from 5V to 12V. The HIP6603B drives both upper and lower gates over a range of 5V to 12V. This drive-voltage flexibility provides the advantage of optimizing applications involving trade-offs between switching losses and conduction losses. The HIP6604B can be configured as either a HIP6601B or a HIP6603B. The output drivers in the HIP6601B, HIP6603B and HIP6604B have the capacity to efficiently switch power MOSFETs at frequencies up to 2MHz. Each driver is capable of driving a 3000pF load with a 30ns propagation delay and 50ns transition time. These products implement bootstrapping on the upper gate with only an external capacitor required. This reduces implementation complexity and allows the use of higher performance, cost effective, N-Channel MOSFETs. Adaptive shoot-through protection is integrated to prevent both MOSFETs from conducting simultaneously. Features • Drives Two N-Channel MOSFETs • Adaptive Shoot-Through Protection • Internal Bootstrap Device • Supports High Switching Frequency - Fast Output Rise Time - Propagation Delay 30ns • Small 8 Ld SOIC and EPSOIC and 16 Ld QFN Packages • Dual Gate-Drive Voltages for Optimal Efficiency • Three-State Input for Output Stage Shutdown • Supply Undervoltage Protection • QFN Package - Compliant to JEDEC PUB95 MO-220 QFN—Quad Flat No Leads—Product Outline. - Near Chip-Scale Package Footprint; Improves PCB Efficiency and Thinner in Profile. • Pb-Free (RoHS Compliant) Applications • Core Voltage Supplies for Intel Pentium® III, AMD® Athlon™ Microprocessors • High Frequency Low Profile DC/DC Converters • High Current Low Voltage DC/DC Converters Related Literature • Technical Brief TB363, Guidelines for Handling and Processing Moisture Sensitive Surface Mount Devices (SMDs)FN9072 Rev 9.00 Page 1 of 14 December 10, 2015

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HIP6601B, HIP6603B, HIP6604BPinouts HIP6601BCB, HIP6603BCB, HIP6601BECB, HIP6603BECB, (8 LD SOIC, EPSOIC) TOP VIEW HIP6604B (16 LD QFN) TOP VIEW Ordering Information PART NUMBER (Notes 1, 2) PART MARKING TEMP. RANGE (°C) PACKAGE (Pb-free) PKG. DWG. # HIP6601BCBZ* 6601 BCBZ 0 to +85 8 Ld SOIC M8.15 HIP6601BCBZA* 6601 BCBZ 0 to +85 8 Ld SOIC M8.15 HIP6601BECBZ* (No longer available or supported) 6601 BECBZ 0 to +85 8 Ld EPSOIC M8.15B HIP6601BECBZA* (No longer available or supported) 6601 BECBZ 0 to +85 8 Ld EPSOIC M8.15B HIP6603BCBZ* 6603 BCBZ 0 to +85 8 Ld SOIC M8.15 HIP6603BECBZ* (No longer available or supported) 6603 BECBZ 0 to +85 8 Ld EPSOIC M8.15B HIP6604BCRZ* (No longer available or supported) 66 04BCRZ 0 to +85 16 Ld QFN L16.4x4 *Add “-T” suffix for tape and reel. Please refer to TB347 for details on reel specifications. NOTES: 1. These Intersil Pb-free plastic packaged products employ special Pb-free material sets, molding compounds/die attach materials, and 100% matte tin plate plus anneal (e3 termination finish, which is RoHS compliant and compatible with both SnPb and Pb-free soldering operations). Intersil Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020. 2. For Moisture Sensitivity Level (MSL), please see device information page for HIP6601B, HIP6603B, HIP6604B. For more information on MSL, please see Technical Brief TB363. UGATE BOOT PWM GND 1 2 3 4 8 7 6 5 PHASE PVCC VCC LGATE 1 3 4 15 NC BOOT PWM GND U G A T E N C P H A S E N C 16 14 13 2 12 10 9 11 65 7 8 NC PVCC LVCC VCC P G N D N C L G A T E N C NO L ON GE R AV AI LA BL E OR S UP PO RT ED FN9072 Rev 9.00 Page 2 of 14 December 10, 2015

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HIP6601B, HIP6603B, HIP6604BAbsolute Maximum Ratings Supply Voltage (VCC) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .15V Supply Voltage (PVCC) . . . . . . . . . . . . . . . . . . . . . . . . . VCC + 0.3V BOOT Voltage (VBOOT - VPHASE) . . . . . . . . . . . . . . . . . . . . . . .15V Input Voltage (VPWM) . . . . . . . . . . . . . . . . . . . . . . GND - 0.3V to 7V UGATE. . . . . . .VPHASE - 5V(<400ns pulse width) to VBOOT + 0.3V . . . . . . . . . . . .VPHASE -0.3V(>400ns pulse width) to VBOOT + 0.3V LGATE . . . . . . . . . GND - 5V(<400ns pulse width) to VPVCC + 0.3V . . . . . . . . . . . . . . GND -0.3V(>400ns pulse width) to VPVCC + 0.3V PHASE. . . . . . . . . . . . . . . . . . GND -5V(<400ns pulse width) to 15V . . . . . . . . . . . . . . . . . . . . . . .GND -0.3V(>400ns pulse width) to 15V ESD Rating Human Body Model (Per MIL-STD-883 Method 3015.7) . . . . .3kV Machine Model (Per EIAJ ED-4701 Method C-111) . . . . . . .200V Thermal Information Thermal Resistance JA (°C/W) JC (°C/W) SOIC Package (Note 3) . . . . . . . . . . . . 97 N/A EPSOIC Package (Note 4). . . . . . . . . . 38 N/A QFN Package (Notes 4, 5). . . . . . . . . . 48 10 Maximum Junction Temperature (Plastic Package) . . . . . . . . 150°C Maximum Storage Temperature Range . . . . . . . . . . -65°C to 150°C Pb-Free Reflow Profile. . . . . . . . . . . . . . . . . . . . . . . . .see link below For Recommended soldering conditions see Tech Brief TB389. Operating Conditions Ambient Temperature Range . . . . . . . . . . . . . . . . . . . . 0°C to 85°C Maximum Operating Junction Temperature . . . . . . . . . . . . . 125°C Supply Voltage, VCC. . . . . . . . . . . . . . . . . . . . . . . . . . . . 12V 10% Supply Voltage Range, PVCC . . . . . . . . . . . . . . . . . . . . . 5V to 12V CAUTION: Do not operate at or near the maximum ratings listed for extended periods of time. Exposure to such conditions may adversely impact product reliability and result in failures not covered by warranty. NOTES: 3. JA is measured with the component mounted on a high effective thermal conductivity test board in free air. See Tech Brief TB379 for details. 4. JA is measured in free air with the component mounted on a high effective thermal conductivity test board with “direct attach” features. See Tech Brief TB379. 5. For JC, the “case temp” location is the center of the exposed metal pad on the package underside. Electrical Specifications Recommended Operating Conditions, Unless Otherwise Noted. Boldface limits apply over the operating temperature range, 0°C to +85°C PARAMETER SYMBOL TEST CONDITIONS MIN (Note 6) TYP MAX (Note 6) UNITS VCC SUPPLY CURRENT Bias Supply Current IVCC HIP6601B, fPWM = 1MHz, VPVCC = 12V - 4.4 6.2 mA HIP6603B, fPWM = 1MHz, VPVCC = 12V - 2.5 3.6 mA Upper Gate Bias Current IPVCC HIP6601B, fPWM = 1MHz, VPVCC = 12V - 200 430 A HIP6603B, fPWM = 1MHz, VPVCC = 12V - 1.8 3.3 mA POWER-ON RESET VCC Rising Threshold 9.7 9.95 10.4 V VCC Falling Threshold 7.3 7.6 8.0 V PWM INPUT Input Current IPWM VPWM = 0V or 5V (See “Block Diagrams” on page 3) - 500 - A PWM Rising Threshold - 3.6 - V PWM Falling Threshold - 1.45 - V UGATE Rise Time tRUGATE VPVCC = 12V, 3nF Load - 20 - ns LGATE Rise Time tRLGATE VPVCC = 12V, 3nF Load - 50 - ns UGATE Fall Time tFUGATE VPVCC = 12V, 3nF Load - 20 - ns LGATE Fall Time tFLGATE VPVCC = 12V, 3nF Load - 20 - ns UGATE Turn-Off Propagation Delay tPDLUGATE VPVCC = 12V, 3nF Load - 30 - ns LGATE Turn-Off Propagation Delay tPDLLGATE VPVCC = 12V, 3nF Load - 20 - ns Shutdown Window 1.4 - 3.6 V Shutdown Holdoff Time - 230 - nsFN9072 Rev 9.00 Page 5 of 14 December 10, 2015

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HIP6601B, HIP6603B, HIP6604BOUTPUT Upper Drive Source Impedance RUGATE VPVCC = 5V - 1.7 3.0  VPVCC = 12V - 3.0 5.0  Upper Drive Sink Impedance RUGATE VPVCC = 5V - 2.3 4.0  VPVCC = 12V - 1.1 2.0  Lower Drive Source Current Equivalent Drive Source Impedance ILGATE RLGATE VPVCC = 5V 400 580 - mA VPVCC = 12V 500 730 - mA VPVCC = 5V - 9 -  Lower Drive Sink Impedance RLGATE VPVCC = 5V or 12V - 1.6 4.0  NOTE: 6. Parameters with MIN and/or MAX limits are 100% tested at +25°C, unless otherwise specified. Temperature limits established by characterization and are not production tested. Electrical Specifications Recommended Operating Conditions, Unless Otherwise Noted. Boldface limits apply over the operating temperature range, 0°C to +85°C PARAMETER SYMBOL TEST CONDITIONS MIN (Note 6) TYP MAX (Note 6) UNITSFN9072 Rev 9.00 Page 6 of 14 December 10, 2015

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HIP6601B, HIP6603B, HIP6604BFunctional Pin Description UGATE (Pin 1), (Pin 16 QFN) Upper gate drive output. Connect to gate of high-side power N-Channel MOSFET. BOOT (Pin 2), (Pin 2 QFN) Floating bootstrap supply pin for the upper gate drive. Connect a bootstrap capacitor between this pin and the PHASE pin. The bootstrap capacitor provides the charge to turn on the upper MOSFET. A resistor in series with boot capacitor is required in certain applications to reduce ringing on the BOOT pin. See “Internal Bootstrap Device” on page 8 for guidance in choosing the appropriate capacitor and resistor values. PWM (Pin 3), (Pin 3 QFN) The PWM signal is the control input for the driver. The PWM signal can enter three distinct states during operation, see the “Three-State PWM Input” on page 8 for further details. Connect this pin to the PWM output of the controller. GND (Pin 4), (Pin 4 QFN) Bias and reference ground. All signals are referenced to this node. PGND (Pin 5 QFN Package Only) This pin is the power ground return for the lower gate driver. LGATE (Pin 5), (Pin 7 QFN) Lower gate drive output. Connect to gate of the low-side power N-Channel MOSFET. VCC (Pin 6), (Pin 9 QFN) Connect this pin to a +12V bias supply. Place a high quality bypass capacitor from this pin to GND. LVCC (Pin 10 QFN Package Only) Lower gate driver supply voltage. PVCC (Pin 7), (Pin 11 QFN) For the HIP6601B and the HIP6604B, this pin supplies the upper gate drive bias. Connect this pin from +12V down to +5V. For the HIP6603B, this pin supplies both the upper and lower gate drive bias. Connect this pin to either +12V or +5V. PHASE (Pin 8), (Pin 14 QFN) Connect this pin to the source of the upper MOSFET and the drain of the lower MOSFET. The PHASE voltage is monitored for adaptive shoot-through protection. This pin also provides a return path for the upper gate drive. Description Operation Designed for versatility and speed, the HIP6601B, HIP6603B and HIP6604B dual MOSFET drivers control both high-side and low-side N-Channel FETs from one externally provided PWM signal. The upper and lower gates are held low until the driver is initialized. Once the VCC voltage surpasses the VCC Rising Threshold (See “Electrical Specifications” on page 5), the PWM signal takes control of gate transitions. A rising edge on PWM initiates the turn-off of the lower MOSFET (see “Timing Diagram” on page 7). After a short propagation delay [tPDLLGATE], the lower gate begins to fall. Typical fall times [tFLGATE] are provided in the “Electrical Specifications” on page 5. Adaptive shoot-through circuitry monitors the LGATE voltage and determines the upper gate delay time [tPDHUGATE] based on how quickly the LGATE voltage drops below 2.2V. This prevents both the lower and upper MOSFETs from conducting simultaneously or shoot-through. Once this delay period is complete the upper gate drive begins to rise [tRUGATE] and the upper MOSFET turns on. Timing Diagram PWM UGATE LGATE tPDLLGATE tFLGATE tPDHUGATE tRUGATE tPDLUGATE tFUGATE tPDHLGATE tRLGATEFN9072 Rev 9.00 Page 7 of 14 December 10, 2015

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HIP6601B, HIP6603B, HIP6604BA falling transition on PWM indicates the turn-off of the upper MOSFET and the turn-on of the lower MOSFET. A short propagation delay [tPDLUGATE] is encountered before the upper gate begins to fall [tFUGATE]. Again, the adaptive shoot-through circuitry determines the lower gate delay time, tPDHLGATE. The PHASE voltage is monitored and the lower gate is allowed to rise after PHASE drops below 0.5V. The lower gate then rises [tRLGATE], turning on the lower MOSFET. Three-State PWM Input A unique feature of the HIP660X drivers is the addition of a shutdown window to the PWM input. If the PWM signal enters and remains within the shutdown window for a set holdoff time, the output drivers are disabled and both MOSFET gates are pulled and held low. The shutdown state is removed when the PWM signal moves outside the shutdown window. Otherwise, the PWM rising and falling thresholds outlined in the Electrical Specifications determine when the lower and upper gates are enabled. Adaptive Shoot-Through Protection Both drivers incorporate adaptive shoot-through protection to prevent upper and lower MOSFETs from conducting simultaneously and shorting the input supply. This is accomplished by ensuring the falling gate has turned off one MOSFET before the other is allowed to rise. During turn-off of the lower MOSFET, the LGATE voltage is monitored until it reaches a 2.2V threshold, at which time the UGATE is released to rise. Adaptive shoot-through circuitry monitors the PHASE voltage during UGATE turn-off. Once PHASE has dropped below a threshold of 0.5V, the LGATE is allowed to rise. PHASE continues to be monitored during the lower gate rise time. If PHASE has not dropped below 0.5V within 250ns, LGATE is taken high to keep the bootstrap capacitor charged. If the PHASE voltage exceeds the 0.5V threshold during this period and remains high for longer than 2s, the LGATE transitions low. Both upper and lower gates are then held low until the next rising edge of the PWM signal. Power-On Reset (POR) Function During initial start-up, the VCC voltage rise is monitored and gate drives are held low until a typical VCC rising threshold of 9.95V is reached. Once the rising VCC threshold is exceeded, the PWM input signal takes control of the gate drives. If VCC drops below a typical VCC falling threshold of 7.6V during operation, then both gate drives are again held low. This condition persists until the VCC voltage exceeds the VCC rising threshold. Internal Bootstrap Device The HIP6601B, HIP6603B, and HIP6604B drivers all feature an internal bootstrap device. Simply adding an external capacitor across the BOOT and PHASE pins completes the bootstrap circuit. The bootstrap capacitor must have a maximum voltage rating above VCC + 5V. The bootstrap capacitor can be chosen from the following equation: Where QGATE is the amount of gate charge required to fully charge the gate of the upper MOSFET. The VBOOT term is defined as the allowable droop in the rail of the upper drive. As an example, suppose a HUF76139 is chosen as the upper MOSFET. The gate charge, QGATE, from the data sheet is 65nC for a 10V upper gate drive. We will assume a 200mV droop in drive voltage over the PWM cycle. We find that a bootstrap capacitance of at least 0.325F is required. The next larger standard value capacitance is 0.33F. In applications which require down conversion from +12V or higher and PVCC is connected to a +12V source, a boot resistor in series with the boot capacitor is required. The increased power density of these designs tend to lead to increased ringing on the BOOT and PHASE nodes, due to faster switching of larger currents across given circuit parasitic elements. The addition of the boot resistor allows for tuning of the circuit until the peak ringing on BOOT is below 29V from BOOT to GND and 17V from BOOT to VCC. A boot resistor value of 5 typically meets this criteria. In some applications, a well tuned boot resistor reduces the ringing on the BOOT pin, but the PHASE to GND peak ringing exceeds 17V. A gate resistor placed in the UGATE trace between the controller and upper MOSFET gate is recommended to reduce the ringing on the PHASE node by slowing down the upper MOSFET turn-on. A gate resistor value between 2 to 10 typically reduces the PHASE to GND peak ringing below 17V. Gate Drive Voltage Versatility The HIP6601B and HIP6603B provide the user total flexibility in choosing the gate drive voltage. The HIP6601B lower gate drive is fixed to VCC [+12V], but the upper drive rail can range from 12V down to 5V depending on what voltage is applied to PVCC. The HIP6603B ties the upper and lower drive rails together. Simply applying a voltage from 5V up to 12V on PVCC will set both driver rail voltages. Power Dissipation Package power dissipation is mainly a function of the switching frequency and total gate charge of the selected MOSFETs. Calculating the power dissipation in the driver for a desired application is critical to ensuring safe operation. Exceeding the maximum allowable power dissipation level will push the IC beyond the maximum recommended operating junction temperature of +125°C. The maximum allowable IC power dissipation for the SO8 package is approximately 800mW. When designing the driver into an application, it is recommended that the following calculation CBOOT QGATE VBOOT ----------------------- (EQ. 1)FN9072 Rev 9.00 Page 8 of 14 December 10, 2015

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HIP6601B, HIP6603B, HIP6604Bbe performed to ensure safe operation at the desired frequency for the selected MOSFETs. The power dissipated by the driver is approximated as: where fsw is the switching frequency of the PWM signal. VU and VL represent the upper and lower gate rail voltage. QU and QL is the upper and lower gate charge determined by MOSFET selection and any external capacitance added to the gate pins. The IDDQ VCC product is the quiescent power of the driver and is typically 30mW. The power dissipation approximation is a result of power transferred to and from the upper and lower gates. But, the internal bootstrap device also dissipates power on-chip during the refresh cycle. Expressing this power in terms of the upper MOSFET total gate charge is explained below. The bootstrap device conducts when the lower MOSFET or its body diode conducts and pulls the PHASE node toward GND. While the bootstrap device conducts, a current path is formed that refreshes the bootstrap capacitor. Since the upper gate is driving a MOSFET, the charge removed from the bootstrap capacitor is equivalent to the total gate charge of the MOSFET. Therefore, the refresh power required by the bootstrap capacitor is equivalent to the power used to charge the gate capacitance of the MOSFET. where QLOSS is the total charge removed from the bootstrap capacitor and provided to the upper gate load. The 1.05 factor is a correction factor derived from the following characterization. The base circuit for characterizing the drivers for different loading profiles and frequencies is provided. CU and CL are the upper and lower gate load capacitors. Decoupling capacitors [0.15F] are added to the PVCC and VCC pins. The bootstrap capacitor value is 0.01F. In Figure 1, CU and CL values are the same and frequency is varied from 50kHz to 2MHz. PVCC and VCC are tied together to a +12V supply. Curves do exceed the 800mW cutoff, but continuous operation above this point is not recommended. Figure 2 shows the dissipation in the driver with 3nF loading on both gates and each individually. Note the higher upper gate power dissipation which is due to the bootstrap device refresh cycle. Again PVCC and VCC are tied together and to a +12V supply. Test Circuit The impact of loading on power dissipation is shown in Figure 3. Frequency is held constant while the gate capacitors are varied from 1nF to 5nF. VCC and PVCC are tied together and to a +12V supply. Figures 4, 5 and 6 show the same characterization for the HIP6603B with a +5V supply on PVCC and VCC tied to a +12V supply. Since both upper and lower gate capacitance can vary, Figure 8 shows dissipation curves versus lower gate capacitance with upper gate capacitance held constant at three different values. These curves apply only to the HIP6601B due to power supply configuration. P 1.05fsw 3 2 --VUQU VLQL+    IDDQVCC+= (EQ. 2) PREFRESH 1 2 -- fSWQLOSSVPVCC 1 2 -- fSWQUVU = = (EQ. 3) BOOT UGATE PHASE LGATEPWM PVCC GND VCC 0.15F 0.15F 100k 2N7002 2N7002 0.01F CL CU +5V OR +12V +12V H IP 6 6 0X +5V OR +12V FIGURE 1. POWER DISSIPATION vs FREQUENCY 1000 800 600 400 200 0 500 1000 1500 2000 P O W E R ( m W ) FREQUENCY (kHz) CU = CL = 3nF VCC = PVCC = 12V CU = CL = 1nF CU = CL = 2nF CU = CL = 4nF CU = CL = 5nF FIGURE 2. 3nF LOADING PROFILE 1000 800 600 400 200 0 500 1000 1500 2000 P O W E R ( m W ) FREQUENCY (kHz) CU = CL = 3nF VCC = PVCC = 12V CU = 3nF CU = 0nF CL = 0nF CL = 3nFFN9072 Rev 9.00 Page 9 of 14 December 10, 2015

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August 6, 2020

Replaced a diode in my distortion pedal. Sounds different (lower growl) but in a good way...LOL!


August 6, 2020

A well designed product that fit my custom PCB's perfectly. Easy to use. Sturdy construction. Highly recommend to all PCB builders.


August 4, 2020

I always enjoy shopping with Heisener, never makes a mistake, most reliable, and no long waiting for deliveries.


July 28, 2020

Not much to say. Nice and cheap, and haven't had a failure yet.


July 27, 2020

Very quick dispatch, arrived the next day. Item as described. Thanks!


July 2, 2020

All current moves in switching devices with the proper selection of amp rating capability. I chose these to do a job that had to handle only 1/3 of it's rated capacity. So they were the perfect choice. To date they work as expected; perfectly.

Ste***** Orr

June 30, 2020

Very fast reply, professional seller and received the correct parts.

Mig***** Lin

June 25, 2020

Fast delivery well packed and as described.


June 23, 2020

This product works great what more can I say.


June 21, 2020

Every little component you can always find in here, and good suggestion for relative times too.

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