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hot TS613ID


For Reference Only

Part Number TS613ID
Manufacturer STMicroelectronics
Description IC OPAMP VFB 130MHZ 8SO
Datasheet TS613ID Datasheet
Package 8-SOIC (0.154", 3.90mm Width)
In Stock 64442 piece(s)
Unit Price Request a Quote
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TS613ID Specifications

CategoryIntegrated Circuits (ICs) - Linear - Amplifiers - Instrumentation, OP Amps, Buffer Amps
Datasheet TS613ID Datasheet
Package8-SOIC (0.154", 3.90mm Width)
Amplifier TypeVoltage Feedback
Number of Circuits2
Slew Rate40 V/µs
Gain Bandwidth Product130MHz
Current - Input Bias5µA
Voltage - Input Offset1mV
Current - Supply11mA
Current - Output / Channel320mA
Voltage - Supply, Single/Dual (��)5 V ~ 12 V, ��2.5 V ~ 6 V
Operating Temperature-40°C ~ 85°C
Mounting TypeSurface Mount
Package / Case8-SOIC (0.154", 3.90mm Width)
Supplier Device Package8-SO

TS613ID Datasheet

Page 1

Page 2

1/10 ■ LOW NOISE : 3nV/√Hz, 1.2pA/√Hz ■ HIGH OUTPUT CURRENT : 200mA ■ VERY LOW HARMONIC AND INTERMODU- LATION DISTORTION ■ HIGH SLEW RATE : 40V/µs ■ SPECIFIED FOR 25Ω LOAD DESCRIPTION The TS613 is a dual operational amplifier featur- ing a high output current (200mA min.), large gain-bandwidth product (130MHz) and capable of driving a 25Ω load with a 160mA output current at ±6V power supply. This device is particularly intended for applications where multiple carriers must be amplified simulta- neously with very low intermodulation products. The TS613 is housed in a SO8 plastic package and a SO8 Exposed-Pad plastic package. APPLICATION ■ UPSTREAM line driver for Asymmetric Digital Subscriber Line (ADSL) (NT). ORDER CODE D = Small Outline Package (SO) - also available in Tape & Reel (DT) DW = Small Outline Package inExposed-Pad (SO) - also available in Tape & Reel (DWT) PIN CONNECTIONS (top view) Part Number Temperature Range Package D DW TS613ID -40, +85°C • TS613IDW -40, +85°C • D SO8 (Plastic Micropackage) DW SO8 Exposed-Pad (Plastic Micropackage) VCC - VCC +1 2 3 54 8 7 6Non Inverting Input1 Inverting Input1 Output2 + _ Output1 Non Inverting Input2 Inverting Input2+ _ Cross Section View Showing Exposed-Pad This pad can be connected to a (-Vcc) copper area on the PCB TS613 DUAL WIDE BAND OPERATIONAL AMPLIFIER WITH HIGH OUTPUT CURRENT December 2002 Ob so let e Pr od uc t(s ) - O bs ole te P ro du ct( s)

Page 3

TS613 2/10 ABSOLUTE MAXIMUM RATINGS OPERATING CONDITIONS Symbol Parameter Value Unit VCC Supply voltage 1) ±7 V Vid Differential Input Voltage 2) ±2 V Vin Input Voltage Range 3) ±6 V Toper Operating Free Air Temperature Range -40 to + 85 °C Tstd Storage Temperature -65 to +150 °C Tj Maximum Junction Temperature 150 °C Output Short Circuit Duration 4) SO8 Rthjc Thermal Resistance Junction to Case 28 °C/W Rthja Thermal Resistance Junction to Ambient Area 175 °C/W Pmax. Maximum Power Dissipation (@25°C) 715 mW SO8 Exposed-Pad Rthjc Thermal Resistance Junction to Case 16 °C/W Rthja Thermal Resistance Junction to Ambient Area 60 °C/W Pmax. Maximum Power Dissipation (@25°C) 2000 mW 1. All voltages values, except differential voltage are with respect to network terminal. 2. Differential voltages are non-inverting input terminal with respect to the inverting input terminal. 3. The magnitude of input and output voltages must never exceed VCC +0.3V. 4. An output current limitation protects the circuit from transient currents. Short-circuits can cause excessive heating. Destructive dissipation can result from short circuit on amplifiers. Symbol Parameter Value Unit VCC Supply Voltage ±2.5 to ±6 V Vicm Common Mode Input Voltage (VCC) +2 to (VCC +) -1 V Ob so let e Pr od uc t(s ) - O bs ole te P ro du ct( s)

Page 4

TS613 3/10 ELECTRICAL CHARACTERISTICS VCC = ±6V, Tamb = 25°C (unless otherwise specified). Symbol Parameter Test Condition Min. Typ. Max Unit DC PERFORMANCE Vio Input Offset Voltage Tamb -6 -1 6 mV Tmin. < Tamb < Tmax. 10 ∆Vio Differential Input Offset Voltage Tamb = 25°C 6 mV Iio Input Offset Current Tamb 0.2 3 µA Tmin. < Tamb < Tmax. 5 Iib Input Bias Current Tamb 5 15 µA Tmin. < Tamb < Tmax. 30 CMR Common Mode Rejection Ratio Vic = ±2V, Tamb 90 108 dB Tmin. < Tamb < Tmax. 70 SVR Supply Voltage Rejection Ratio Vic = ±6V to ±4V, Tamb 70 88 dB Tmin. < Tamb < Tmax. 50 ICC Total Supply Current per Operator No load, Vout = 0 11 mA DYNAMIC PERFORMANCE and OUTPUT CHARACTERISTICS VOH High Level Output Voltage Iout = 160mA, RL to GND 4 4.5 V VOL Low Level Output Voltage Iout = 160mA, RL to GND -4.5 -4 V AVD Large Signal Voltage Gain Vout = 7V peak RL = 25Ω, Tamb 6500 11000 V/V Tmin. < Tamb < Tmax. 5000 GBP Gain Bandwidth Product AVCL = +11, f = 20MHz RL = 100Ω 80 130 MHz SR Slew Rate AVCL = +7, RL = 50Ω 23 40 V/µs Isink Isource Output Short Circuit Current Vid = ±1V, Tamb ±200 ±320 mA Tmin. < Tamb < Tmax. ±180 ΦM14 Phase Margin at AVCL = 14dB RL = 25Ω//15pF 60 ° ΦM6 Phase Margin at AVCL = 6dB RL = 25Ω//15pF 40 ° NOISE AND DISTORTION en Equivalent Input Noise Voltage f = 100kHz 3 nV/√Hz in Equivalent Input Noise Current f = 100kHz 1.2 pA/√Hz THD Total Harmonic Distortion Vout = 4Vpp, f = 100kHz AVCL = -10 RL = 25Ω//15pF -69 dB HD2-10 2nd Harmonic Distortion Vout = 4Vpp, f = 100kHz AVCL = -10 Load =25Ω//15pF -70 dBc HD2+2 2nd Harmonic Distortion Vout = 4Vpp, f = 100kHz AVCL = +2 Load =25Ω//15pF -74 dBc HD3-10 3rd Harmonic Distortion Vout = 4Vpp, f = 100kHz AVCL = -10 Load =25Ω//15pF -80 dBc HD3+2 3rd Harmonic Distortion Vout = 4Vpp, f = 100kHz AVCL = +2 Load =25Ω//15pF -79 dBc IM2-10 2nd Order Intermodulation Product F1 = 80kHz, F2 = 70kHz Vout = 8Vpp, AVCL = -10 Load = 25Ω//15pF -77 dBc IM3-10 3rd Order Intermodulation Product F1 = 80kHz, F2 = 70kHz Vout = 8Vpp, AVCL = -10 Load = 25Ω//15pF -77 dBc Ob so let e Pr od uc t(s ) - O bs ole te P ro du ct( s)

Page 5

TS613 4/10 THERMAL INFORMATION The TS613 is housed in an Exposed-Pad plastic package. As described on the figures below, this package uses a leadframe upon which the dice is mounted. This leadframe is exposed as a thermal pad on the underside of the package. The thermal contact is direct with the dice. This thermal path provide an excellent thermal performance. The thermal pad is electrically isolated from all pins in the package. It can also be soldered to a copper area of the PCB underneath the package. Through these thermal paths within this copper ar- ea, heat can be conducted away from the pack- age. In this case, the copper area must be con- nected to (-Vcc) INTERMODULATION DISTORTION The curves shown below are the measurements results of a single operator wired as an adder with a gain of 15dB. The operational amplifier is supplied by a symmet- ric ±6V and is loaded with 25Ω. Two synthesizers (Rhode & Schwartz SME) gen- erate two frequencies (tones) (70 & 80kHz ; 180 & 280kHz). An HP3585 spectrum analyzer measures the spu- rious level at different frequencies. The curves are traced for different output levels (the value in the X ax is the value of each tone). The output levels of the two tones are the same. The generators and spectrum analyzer are phase locked to enhance measurement precision. 3rd ORDER INTERMODULATION Gain=15dB, Vcc=±6V, RL=25Ω, 2 tones 70kHz/ 80kHz 2nd ORDER INTERMODULATION Gain=15dB, Vcc=±6V, RL=25Ω, 2 tones 180kHz/ 280kHz, Spurious measurement @100kHz 3rd ORDER INTERMODULATION Gain=15dB, Vcc=±6V, RL=25Ω, 2 tones 180kHz/ 280kHz Cross Section View DICE Bottom View D IC E Side View 1 1,5 2 2,5 3 3,5 4 4,5 -100 -90 -80 -70 -60 -50 -40 -30 -20 -10 0 IM 3 (d B c ) Vout peak (V) 230kHz 220kHz 90kHz 60kHz Vout peak (V) 1,5 2 2,5 3 3,5 4 4,5 -70 -65 -60 -55 IM 2 ( d B c ) 1 1,5 2 2,5 3 3,5 4 4,5 -100 -90 -80 -70 -60 -50 -40 -30 -20 -10 0 IM 3 (d B c ) Vout peak (V) 80kHz 640kHz 380kHz 740kHz Ob so let e Pr od uc t(s ) - O bs ole te P ro du ct( s)

Page 6

TS613 5/10 Closed Loop Gain and Phase vs. Frequency Gain=+2, Vcc=±6V, RL=25Ω Closed Loop Gain and Phase vs. Frequency Gain=+11, Vcc=±6V, RL=25Ω Maximum Output Swing Vcc=±6V, RL=25Ω Closed Loop Gain and Phase vs. Frequency Gain=+6, Vcc=±6V, RL=25Ω Equivalent Input Voltage Noise Gain=+100, Vcc=±6V, no load Channel Separation (Xtalk) vs. Frequency XTalk=20Log(V2/V1), Vcc=±6V, RL=25Ω -30 -20 -10 0 10 G a in (d B ) -200 -100 0 100 200 P h a s e (d e g re e s ) 10kHz 100kHz 1MHz 10MHz 100MHz Frequency Gain Phase -30 -20 -10 0 10 20 30 G a in (d B ) -200 -100 0 100 200 P h a s e (d e g re e s ) 10kHz 100kHz 1MHz 10MHz 100MHz Frequency Gain Phase 0 2 4 6 8 10 Time (µs) -5 -4 -3 -2 -1 0 1 2 3 4 5 s w in g ( V ) output input -20 -15 -10 -5 0 5 10 15 20 G a in (d B ) -200 -100 0 100 200 P h a s e (d e g re e s ) 10kHz 100kHz 1MHz 10MHz 100MHz Frequency Gain Phase 100Hz 1kHz 10kHz 100kHz 1MHz 0 5 10 15 20 e n ( n V /V H z ) _ + 100 10k Frequency -80 -70 -60 -50 -40 -30 -20 X ta lk (d B ) 10kHz 100kHz 1MHz 10MHz Frequency 100Ω + _ 1kΩ 49.9Ω V1 VIN 100Ω + _ 1kΩ 49.9Ω V2 25Ω 25Ω Ob so let e Pr od uc t(s ) - O bs ole te P ro du ct( s)

Page 7

6/10 ADSL CONCEPT Asymmetric Digital Subscriber Line (ADSL), is a new modem technology, which converts the exist- ing twisted-pair telephone lines into access paths for multimedia and high speed data communica- tions. ADSL transmits more than 8 Mbps to a subscriber, and can reach 1Mbps from the subscriber to the central office. ADSL can literally transform the ac- tual public information network by bringing mov- ies, television, video catalogs, remote CD-ROMs, LANs, and the Internet into homes. An ADSL modem is connected to a twisted-pair telephone line, creating three information chan- nels: a high speed downstream channel (up to 1.1MHz) depending on the implementation of the ADSL architecture, a medium speed upstream channel (up to 130kHz) and a POTS (Plain Old Telephone Service), split off from the modem by filters. THE LINE INTERFACE - ADSL Remote Terminal (RT): The Figure1 shows a typical analog line interface used for ADSL. The upstream and downstream signals are separated from the telephone line by using an hybrid circuit and a line transformer. On this note, the accent will be made on the emission path. The TS613 is used as a dual line driver for the up- stream signal. For the remote terminal it is required to create an ADSL modem easy to plug in a PC. In such an ap- plication, the driver should be implemented with a +12 volts single power supply. This +12V supply is available on PCI connector of purchase. The figure 2 shows a single +12V supply circuit that uses the TS613 as a remote terminal trans- mitter in differential mode. The driver is biased with a mid supply (nominaly +6V), in order to maintain the DC component of the signal at +6V. This allows the maximum dy- namic range between 0 and +12 V. Several op- tions are possible to provide this bias supply (such as a virtual ground using an operational amplifier), such as a two-resistance divider which is the cheapest solution. A high resistance value is re- quired to limit the current consumption. On the other hand, the current must be high enough to bias the inverting input of the TS613. If we consid- er this bias current (5µA) as the 1% of the current through the resistance divider (500µA) to keep a stable mid supply, two 47kΩ resistances can be used. The input provides two high pass filters with a break frequency of about 1.6kHz which is neces- sary to remove the DC component of the input sig- nal. To avoid DC current flowing in the primary of the transformer, an output capacitor is used. The Figure 1 : Typical ADSL Line Interface impedance matching twisted-pair telephone line HYBRID CIRCUIT digital treatment LP filter TS613 Line Driver reception (analog) emission (analog) digital to analog analog to digital high output current reception circuits upstream downstream Figure 2 : TS613 as a differential line driver with a +12V single supply 1/2 R1 R3 R2 Vi Vi Vo Vo GND +12V 25Ω 100Ω 1:2 Hybrid & Transformer GND +12V 47k 47k10µ 100n 100n 100n 1k 1k 12.5 12.5 10n 1µ +12V + _ + _ GND 1/2 R1 Vcc/2 TYPICAL APPLICATION : TS613 AS DRIVER FOR ADSL LINE INTERFACES by C. PRUGNE A SINGLE SUPPLY IMPLEMENTATION WITH PASSIVE OR ACTIVE IMPEDANCE MATCHING Ob ole te P ro du ct( s) - Ob so let e Pr od uc t(s )

Page 8

TS613 7/10 1µF capacitance provides a path for low frequen- cies, the 10nF capacitance provides a path for high end of the spectrum. In differential mode the TS613 is able to deliver a typical amplitude signal of 18V peak to peak. The dynamic line impedance is 100Ω. The typical value of the amplitude signal required on the line is up to 12.4V peak to peak. By using a 1:2 trans- former ratio the reflected impedance back to the primary will be a quarter (25Ω) and therefore the amplitude of the signal required with this imped- ance will be the half (6.2 V peak to peak). Assum- ing the 25Ω series resistance (12.5Ω for both out- puts) necessary for impedance matching, the out- put signal amplitude required is 12.4 V peak to peak. This value is acceptable for the TS613. In this case the load impedance is 25Ω for each driv- er. For the ADSL upstream path, a lowpass filter is absolutely necessary to cutoff the higher frequen- cies from the DAC analog output. In this simple non-inverting amplification configuration, it will be easy to implement a Sallen-Key lowpass filter by using the TS613. For ADSL over POTS, a maxi- mum frequency of 135kHz is reached. For ADSL over ISDN, the maximum frequency will be 276kHz. INCREASING THE LINE LEVEL BY USING AN ACTIVE IMPEDANCE MATCHING With passive matching, the output signal ampli- tude of the driver must be twice the amplitude on the load. To go beyond this limitation an active maching impedance can be used. With this tech- nique it is possible to keep good impedance matching with an amplitude on the load higher than the half of the ouput driver amplitude. This concept is shown in figure3 for a differential line. Component calculation: Let us consider the equivalent circuit for a single ended configuration, figure4. Let us consider the unloaded system. Assuming the currents through R1, R2 and R3 as respectively: As Vo° equals Vo without load, the gain in this case becomes : The gain, for the loaded system will be (1): As shown in figure5, this system is an ideal gener- ator with a synthesized impedance as the internal impedance of the system. From this, the output voltage becomes: with Ro the synthesized impedance and Iout the output current. On the other hand Vo can be ex- pressed as: Figure 3 : TS613 as a differential line driver with an active impedance matching R4 R2 Vi Vi Vo Vo RL 100Ω 1:n Hybrid & Transformer GND Vcc+ 10µ 100n 100n 100n 1k 1k Rs1 Rs2 10n 1µ R3 R5 Vo° Vo° GND Vcc+ Vcc+ + _ + _ GND 1/2 R1 1/2 R1 Vcc/2 Figure 4 : Single ended equivalent circuit 1/2R1 R2 R3 + _Vi Vo Rs1 -1 Vo° 1/2RL 2Vi R1 -------- Vi Vo°–( ) R2 ------------------------- and Vi Vo+( ) R3 -----------------------, G Vo noload( ) Vi ------------------------------ 1 2R2 R1 ---------- R2 R3 ------+ + 1 R2 R3 ------– ----------------------------------= = GL Vo withload( ) Vi ----------------------------------- 1 2 -- 1 2R2 R1 ---------- R2 R3 ------+ + 1 R2 R3 ------– ---------------------------------- 1( ),= = Vo ViG( ) RoIout( )–= 2( ), Vo Vi 1 2R2 R1 ---------- R2 R3 ------+ +    1 R2 R3 ------– ---------------------------------------------- Rs1Iout 1 R2 R3 ------– --------------------- 3( ),–= Ob so let e Pr od uc t(s ) - O b let e Pr du ct( s)

Page 9

TS613 8/10 By identification of both equations (2) and (3), the synthesized impedance is, with Rs1=Rs2=Rs: Unlike the level Vo° required for a passive imped- ance, Vo° will be smaller than 2Vo in our case. Let us write Vo°=kVo with k the matching factor vary- ing between 1 and 2. Assuming that the current through R3 is negligeable, it comes the following resistance divider: After choosing the k factor, Rs will equal to 1/2RL(k-1). A good impedance matching assumes: From (4) and (5) it becomes: By fixing an arbitrary value for R2, (6) gives: Finally, the values of R2 and R3 allow us to extract R1 from (1), and it comes: with GL the required gain. CAPABILITIES The table below shows the calculated compo- nents for different values of k. In this case R2=1000Ω and the gain=16dB. The last column displays the maximum amplitude level on the line regarding the TS613 maximum output capabilities (18Vpp diff.) and a 1:2 line transformer ratio. MEASUREMENT OF THE POWER CONSUMPTION IN THE ADSL APPLICATION Conditions: Passive impedance matching Transformer turns ratio: 2 Power Supply: 12V Maximun level required on the line: 12.4Vpp Maximum output level of the driver: 12.4Vpp Crest factor: 5.3 (Vp/Vrms) The TS613 power consumption during emission on 900 and 4550 meter twisted pair telephone lines: 360mW Figure 5 : Equivalent schematic. Ro is the syn- thesized impedance Ro Rs 1 R2 R3 ------– ---------------- 4( ),= Ro Vi.Gi Iout 1/2RL Ro kVoRL RL 2Rs1+ ---------------------------= Ro 1 2 -- RL 5( ),= R2 R3 ------ 1 2Rs RL --------- 6( ),–= R3 R2 1 2Rs RL ---------– -------------------= R1 2R2 2 1 R2 R3 ------–    GL 1– R2 R3 ------– --------------------------------------------------------- 7( ),= GL (gain for the loaded system) GL is fixed for the application requirements GL=Vo/Vi=0.5(1+2R2/R1+R2/R3)/(1-R2/R3) R1 2R2/[2(1-R2/R3)GL-1-R2/R3] R2 (=R4) Abritrary fixed R3 (=R5) R2/(1-Rs/0.5RL) Rs 0.5RL(k-1) Active matching k R1 (Ω) R3 (Ω) Rs (Ω) TS613 Output Level to get 12.4Vpp on the line (Vpp diff) Maximum Line level (Vpp diff) 1.3 820 1500 3.9 8 27.5 1.4 490 1600 5.1 8.7 25.7 1.5 360 2200 6.2 9.3 25.3 1.6 270 2400 7.5 9.9 23.7 1.7 240 3300 9.1 10.5 22.3 Passive matching 12.4 18 Ob so let e Pr od uc t(s ) - O bs ole te P ro du ct( s)

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TS613 9/10 PACKAGE MECHANICAL DATA 8 PINS - PLASTIC MICROPACKAGE (SO) Dim. Millimeters Inches Min. Typ. Max. Min. Typ. Max. A 1.75 0.069 a1 0.1 0.25 0.004 0.010 a2 1.65 0.065 a3 0.65 0.85 0.026 0.033 b 0.35 0.48 0.014 0.019 b1 0.19 0.25 0.007 0.010 C 0.25 0.5 0.010 0.020 c1 45° (typ.) D 4.8 5.0 0.189 0.197 E 5.8 6.2 0.228 0.244 e 1.27 0.050 e3 3.81 0.150 F 3.8 4.0 0.150 0.157 L 0.4 1.27 0.016 0.050 M 0.6 0.024 S 8° (max.) Ob so let e Pr od uc t(s ) - O bs ole te P ro du ct( s)

TS613ID Reviews

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January 3, 2020

Super easy to replace and labelled terminals made it a quick replacement.


January 2, 2020

I am very happy with how Heisener do business. Will definitely buy their products in the future as I have confidence in their customer service.


August 12, 2019

It works fine and does what it has designed for. No regrets.


July 28, 2019

I always enjoy shopping with Heisener, never disappoint me, most dependable, and no long waiting for deliveries.


July 7, 2019

It gives you a good quality product, with a great variety.. I will for sure order this set again when i start to run low.


July 2, 2019

I've made a few purchases from Heisener and always get a friendly technician helped me with locate what I was looking for. That kind of attitude is greatly appreciated.


March 24, 2019

I am satisfied with Heisener company


March 15, 2019

Excellent website experience for search any product I want, problem solvers. You guys I can trust and reply on.


February 14, 2019

As I said before, your crew rock's keep up the fantastic work as we need you out there.


February 8, 2019

Comparison with other company, Heisener is my first choice for supplier.

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